Clock control circuit and method

ABSTRACT

A clock controlling circuit and method for eliminating the delay difference in the entire clock propagation line. Circuit scale is reduced as compared to a case of using a PLL or DLL circuit. A timing averaging circuit  10  is fed with clocks from a position on a forward route  11   1  of a direction-reversed clock propagation path, adapted for being fed with input clocks at its one end, and from a position on a return route  11   2  corresponding to the position on the forward route  11   1 . 
     The timing difference between these clocks is averaged to output an averaged timing difference.

The present Application is a Divisional Application of U.S. patentapplication Ser. No. 10/330,275, filed on Dec. 30, 2002 now U.S. Pat.No. 6,771,107 which was a Divisional Application of U.S. patentapplication Ser. No. 09/842,200 filed on Apr. 26, 2001 now U.S. Pat. No.6,525,588.

FIELD OF THE INVENTION

This invention relates to a clock controlling circuit and a clockcontrolling method. More particularly, it relates to a clock controllingcircuit and a clock controlling method usable with advantage in a clocksupplying circuit of a semiconductor integrated circuit having a circuitsynchronized with system clocks.

BACKGROUND OF THE INVENTION

In a semiconductor integrated circuit controlling the internal circuitin synchronism with system clocks, preset circuit operations areexecuted each clock period to control the internal circuit in itsentirety. Recently, the chip size is increased in keeping pace with thetendency towards the increasing degree of integration and towards thehigher function of the function of the semiconductor integrated circuit.On the other hand, as the clock period becomes shorter with theincreasing operating frequency, the shortening of the delay timedifference in the clock path is presenting problems.

In order to cope with this task, there is disclosed in, for example, theJP Patent Kokai JP-A-9-258841 a clock supplying method in which thereare provided an oncoming clock line and an outgoing clock line, theseclock lines are divided into two lines of forward and return paths, andin which the wiring delay is detected to adjust clocks. There isdisclosed a configuration comprising a receiver having first and secondinput terminals at a first position on the forward path and a secondposition near the first position on the forward path, respectively. Thedelay in the forward path and return path is detected from these firstand second input terminals to output an average value of the delaycaused in the forward and return paths.

That is, in the JP Patent Kokai JP-A-9-258841, a point A of a forwardroute 111, as an input, is coupled to an end of a phase detectioncircuit 181 through a variable delay line 171 and a variable delay line172, a point H of a return route 112, as an input, is coupled to theother end of the phase detection circuit 181, the delay time of thevariable delay lines 171, 172 is variably controlled for phaseadjustment, and an output of a receiver is derived from a junction pointof the variable delay lines 171, 172.

Since the delay time from the point A of the forward route 111 of theclock propagation path up to a turning point 113 is a, the delay timefrom the point A to the point H is 2a, an average value of the delaytime between the points A and H is a, the delay time from the point b ofthe forward route 111 of the clock transmitting line to the turningpoint 113 is b and the delay time from the point B to the point G is 2b.So, the sum of the delay time (a−b) from the input end to the point band the delay time ((a−b)+(a−b)+2b) from the input end to the point G is{(a−b)+((a−b)+(a−b)+2b)} is 2a, with an average value being a. In thismanner, clock signals with the corresponding phase can be obtainedwithout dependency on the positions of the clock propagation path.

In this manner, in the conventional method disclosed in the JP PatentKokai JP-A-9-258841, a clock path is direction-reversed and a delaytiming of an intermediate point between the forward and return routes istaken to adjust the delay amount of the variable delay line in the clockpath.

For adjusting the delay in this manner, a feedback circuit loop,exemplified by a phase locked loop (PLL) or a delay lock loop (DLL), inwhich the phase difference is detected by a phase detection circuit andthe delay caused in the variable delay line is varied based on thedetected phase difference, is routinely used.

SUMMARY OF THE DISCLOSURE

However, the PLL or DLL, constituting a feedback circuit, presents aproblem that a period longer by about hundreds to thousands of cycles isneeded until clock stabilization is achieved.

There is also raised a problem that plural sets of the phase comparatorsand delay circuit lines are needed thus increasing the circuit scale.

In view of the aforementioned problems, it is an object of the presentinvention to provide a clock controlling circuit and a clock controlmethod for a circuit for eliminating the delay difference in the entireclock transmitting line, according to which the delay difference may beeliminated in a shorter time than the case where the PLL circuit or theDLL circuit is used.

It is another object of the present invention to provide a clockcontrolling circuit and a clock control method according to which aphase comparator may be eliminated to prevent the circuit scale fromincreasing.

According to a first aspect of the present invention, there is provideda clock controlling circuit comprising:

a timing difference dividing circuit for receiving a clock at a firstposition on a forward route of a clock propagation pathdirection-reversing input clocks fed at one end thereof, and a clock ata second position on a return route thereof corresponding to the firstposition on the forward route,

the timing difference dividing circuit outputting a signal of a delaytime corresponding to a time obtained on dividing a timing difference ofthe two clocks by a preset interior division ratio.

According to a second aspect of the present invention, there is provideda clock controlling circuit comprising:

a timing difference averaging circuit for receiving a clock at a firstposition on a forward route of a clock propagation pathdirection-reversing input clocks fed at one end thereof, and a clock ata second position on a return route thereof corresponding to the firstposition on the forward route,

the timing difference dividing circuit outputting a signal of a delaytime corresponding to a time obtained on evenly dividing a timingdifference of the two clocks.

According to a third aspect of the present invention, the timingaveraging circuit is configured to issue an output signal with a delaytime equal to the sum of a first delay time until output signal isissued after one of the two input clocks undergoing transition at anearlier time point is input simultaneously to first and second inputsadapted for being fed with the two clocks and a second delay timecorresponding to a time (T/2) obtained on dividing the timing differenceT of said two clocks into two equal portions.

According to a fourth aspect of the present invention, there is provideda timing averaging circuit fed with clocks from a first position on aforward route of a clock propagation path, adapted fordirection-reversing clocks frequency divided by a frequency dividingcircuit and input at an end of the clock propagation path and from asecond position on a return route thereof corresponding to the firstposition on the forward route, and a multiplication circuit formultiplying an output of the timing averaging circuit.

According to a fifth aspect of the present invention, there is provideda clock controlling circuit comprising:

a timing averaging circuit provided with a frequency dividing functionfor frequency dividing two, first and second, clocks, i.e., the firstclock from a first position on a forward route of a clock propagationpath fed with input clocks at one end and direction-reversing the inputclocks and the second clock from a second position corresponding to thefirst position to generate frequency divided multi-phase clocks ofplural different phases,

the timing averaging circuit outputting a signal of a delay timecorresponding to a time equally dividing a timing difference betweenfrequency divided clocks having a corresponding phase among clocksignals obtained on frequency division of the two clocks; and

a synthesis circuit for synthesizing plural outputs of the timingaveraging circuits into one signal and for outputting the one signal.

According to a sixth aspect of the present invention, there is provideda clock controlling method, averages the timing difference of clockstaken from a first position on a forward route of a clock propagationpath fed with input clocks at one end and direction-reversing the inputclocks and from a second position on a return route corresponding to thefirst position on the forward route to generate a clock or clocks withmatched clock timing irrespective of the clock taking positions on theforward and return route.

Other aspects and features of the present invention are disclosed alsoin the claims, the entire disclosure thereof being incorporated hereinby reference thereto.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 shows the structure of an embodiment of the present invention.

FIG. 2 is a timing chart for illustrating the operation of theembodiment of the present invention.

FIG. 3 shows the structure of a timing averaging circuit embodying thepresent invention.

FIG. 4 shows the operation of a timing averaging circuit embodying thepresent invention.

FIG. 5 shows the structure of a second embodiment of the presentinvention.

FIG. 6 shows the structure of another exemplary timing averaging circuitembodying the present invention.

FIG. 7 shows the structure of another exemplary timing averaging circuitembodying the present invention.

FIG. 8 shows the structure of another exemplary timing averaging circuitembodying the present invention.

FIG. 9 shows the structure of a third embodiment of the presentinvention.

FIG. 10 is a timing chart for illustrating the operation of the thirdembodiment of the present invention.

FIG. 11 shows an exemplary structure of a multiplication circuit of thethird embodiment of the present invention.

FIG. 12 shows an exemplary structure of a multi-phase clockmultiplication circuit shown in FIG. 11.

FIG. 13 shows an illustrative structure of the multi-phase clockmultiplication circuit.

FIG. 14 is a timing chart for illustrating the operation of themulti-phase clock multiplication circuit.

FIG. 15 shows an illustrative structure of timing difference dividingcircuits 208, 209 of a four-phase clock multiplication circuit of FIG.13.

FIG. 16 shows a structure of a fourth embodiment of the presentinvention.

FIG. 17 shows a structure of a timing averaging circuit provided with afrequency dividing function.

FIG. 18 is a timing chart for illustrating the operation of the fourthembodiment of the present invention.

FIG. 19 shows a structure of a fifth embodiment of the presentinvention.

FIG. 20 is a timing chart for illustrating the operation of the fifthembodiment of the present invention.

FIG. 21 shows a structure of the fifth embodiment of the presentinvention.

FIG. 22 shows an exemplary structure of a conventional clock controllingcircuit.

PREFERRED EMBODIMENTS OF THE INVENTION

A preferred embodiment of the present invention is explained. In itspreferred embodiment, shown in FIG. 1, the present invention includes atiming averaging circuit which is fed with clocks from a first positionon a forward route of a clock propagation path adapted for being fedwith input clocks at one end and direction-reversing the input clocksand from a second position on a return route corresponding to the firstposition on the forward route and which divides the timing difference ofthese clocks into two equal portions to output the resulting clocks. Thedelay time between the first position and the direction-reversing point11 ₃ of the clock propagation path is equal to the delay time betweenthe direction-reversing point 11 ₃ of the clock propagation path and thesecond position.

The timing averaging circuit issues an output signal with a delay timeequal to the sum of a (first) delay time (Cons) until outputting of anoutput signal after one of the two input clocks undergoing transition atan earlier time is input simultaneously to the first and second inputends fed with the two clocks and a (second) delay time corresponding toa time (T/2) obtained on dividing the timing difference T of the twoclocks into two equal portions. Namely, the present invention does notuse PLL nor DLL. The timing averaging circuit is configured so that theinternal node is charged or discharged, based on one of two input clocksthat undergoes an earlier transition and so that the internal load ischarged or discharged based on the other clock undergoing be latertransition and the aforementioned one clock. The internal node isconnected to the input end. There is provided an inverting ornon-inverting buffer circuit an output logical value of which is changedwhen the internal node voltage becomes higher or lower than a thresholdvoltage.

In its preferred embodiment of the present invention, shown in FIG. 5,input clocks are input from one end of a clock propagation path andbranches to first and second forward routes (11A, 11B), with the firstand second forward routes being direction-reversed (preferably, in acrossing fashion) on an opposite end to the said one end, with thereturn routes (11C, 11D) of the first and second routes thusdirection-reversed being arranged along the forward routes (11A, 11B) ofthe second and first routes. The clock controlling circuit includestiming averaging circuits 10 ₁, 10 ₂ for being fed with a clock fromfirst positions (A, B) on the forward route 11A of the first route andwith a clock from the second position (C, D) on the return route 11D ofthe second route for outputting a signal of delay time corresponding tothe time averaging a timing difference between the clocks in two equalportions, and timing averaging circuits 10 ₄, 10 ₃ for being fed withclocks from third positions E, F on a forward route 11 b of the secondroute and from fourth positions D, C on the return route 11C of thesecond route to average out the timing difference of these clocks tooutput the resulting clocks.

In a preferred embodiment of the present invention, shown in FIG. 9,there are provided a frequency dividing circuit 14 for frequencydividing input clocks, timing averaging circuits 10 ₁, 10 ₂, 10 ₃, 10 ₄for being fed with clocks from first positions A, B, C and D on aforward route of a clock propagation path adapted for being fed withclocks frequency divided by the frequency dividing circuit, the pathdirection-reversing the clocks, and second positions H, G, E and F on areturn route corresponding to the first position on the forward route,the timing averaging circuit outputting a signal of a delay timecorresponding to a time dividing a timing difference of these clocks intwo equal portions, and multiplication circuits 15 ₁, 15 ₂, 15 ₃, 15 ₄for multiplying an output signal from the timing averaging circuits 10₁, 10 ₂, 10 ₃, 10 ₄ and outputting a multiplied output signal.

In a preferred embodiment of the present invention, shown in FIG. 16,there are provided timing averaging circuits provided with frequencydividing functions (function units) 100 ₁ to 100 ₄ fed with two clocksfrom first positions A, B, C and D on a forward route 11 ₁ of the clockpropagation path and from second positions H, G, F, E corresponding tothe first positions on the forward route, and synthesis circuits 16 ₁ to16 ₄ for synthesizing plural outputs (L1 to L4, K1 to k4, J1 to J4 andI1 to I4)of the timing averaging circuits provided with the frequencydividing function 100 ₁ to 100 ₄ into one signal and for outputting theone signal.

The timing averaging circuit provided with the frequency dividingfunction has first and second frequency dividing circuits 101 ₁, 101 ₂for frequency dividing two clocks to output plural frequency dividedclocks having respective different phases, a plurality of timingaveraging circuits 102 ₁ to 102 ₄ for being fed with two frequencydivided clocks of the first and the second frequency dividing circuitshaving corresponding phases and a synthesis circuit 16 for synthesizingplural outputs L1 to L4 of the timing averaging circuits 102 ₁ to 102 ₄into one signal.

In a preferred embodiment of the present invention, shown in FIG. 19,there are provided a frequency dividing circuit 14A for frequencydividing input clocks for outputting frequency divided clocks of pluraldifferent phases, a plurality of clock propagation paths 11-1 to 11-4for being fed at one end with a plurality of frequency divided clocksoutput from the frequency dividing circuit, a plurality of timingaveraging circuits (four TMs) for being fed with two clocks from a firstposition on the forward route and from a second position on a returnroute associated with the first position, for each of the plural clockpropagation paths, to output signals of delay time corresponding to thetime resulting from division of a timing difference of the two clocksinto two equal portions, and a synthesis circuit 16 for synthesizingplural outputs of the plural timing averaging circuits (four TMs).

In a preferred embodiment of the present invention, shown in FIG. 21,there are provided timing averaging circuits 110 ₁ to 110 ₄ for beingfed with two clocks from first positions A to D on a forward route of aclock propagation path 111, and from second positions H, G, F and E onthe return route corresponding to the position on the forward route, andtiming averaging circuits 120 ₁ to 120 ₄ for being fed with two clocksfrom a certain position on the forward route of the second clockpropagation path 114 ₁, and from a position on the return routecorresponding to the position on the forward route.

There are also provided timing averaging circuits 121 ₁ to 121 ₄ forbeing fed with two clocks from a certain position on a forward route ofa second clock propagation path 114 ₂, fed with clocks output from thetiming averaging circuits 110 ₂ at one end for direction-reversing theclocks and from a position on the return route corresponding to theposition on the forward route, timing averaging circuits 122 ₁ to 122 ₄for being fed with two clocks from a certain position on a forward routeof a second clock propagation path 114 ₃, fed with clocks output fromthe timing averaging circuits 110 ₃ at one end for direction-reversingthe clocks, and from a position on the return route corresponding to theposition on the forward route, and timing averaging circuits 123 ₁ to123 ₄ for being fed with two clocks from a certain position on a forwardroute of a second clock propagation path 114 ₄, and from a position onthe return route corresponding to the position on the forward route. Theoutput signals of these timing averaging circuits are arranged e.g., ina mesh-like fashion on a two-dimensional plane of a semiconductorintegrated circuit or a printed wiring board.

A few circuit configurations of the timing averaging circuits arehereinafter explained. The timing averaging circuit in a preferredembodiment of the present invention for being fed with clocks on forwardand return routes of the direction-reversing type clock propagationpath, shown in FIG. 3, includes first and second switch elements MP1,MP2 connected in parallel across the first power source and an internalnode and which are turned on and off when the first and second inputsIN1, IN2 are at first and second values, respectively, a third switchelement MN1 connected across the internal node N1 and a second powersource GND, the third switch element being fed on a control terminalwith an output of a logic circuit NOR fed with the first and secondinputs, and being turned on when the first and second inputs are at thesecond value, a capacitance C connected across the internal node N1 anda second power source GND and a buffer circuit BUT an output logicalvalue of which is determined based on the relative magnitudes of thepotential of the internal node N1 and the threshold value.

In a preferred embodiment of the present invention, shown in FIG. 6, thetiming averaging circuit includes a plurality of first switch elementsMP1, MP2 connected in series across a first power source VCC and aninternal node N52, the timing averaging circuit having its controlterminal fed with a first input IN1 and being turned off when the firstinput IN1 is at a first value, a plurality of second switch elementsMN51, MN52 connected in series across the internal node N52 and a secondpower source GND, each second switch element having its control terminalconnected to the first input IN1 and being turned on when the firstinput IN1 is at a first value, a third switch element MP53 connected inseries across the first power source and a second power source N52, thefourth switch element having its control terminal connected to the firstinput IN1, and being turned off when the first input IN1 is at a firstvalue, a fourth switch element MP54 having its control terminalconnected to the second input IN2 and being turned off when the secondinput IN2 is at a first value, a fifth switch element MN54 connected inseries across the internal node N52 and the second power source, thefifth switch element having its control terminal connected to the firstinput, and being turned on when the first input is at a first value, anda sixth switch element MN53 having its control terminal connected to thesecond input and being turned on when the second input is at the firstvalue and an inverter circuit INV51 an output logical value of which isdetermined based on the relative magnitudes of the internal node and athreshold value. The switch elements MP55, MP56, control terminals whichare connected to the second input, are connected to the first powersource, the switching elements MN55 MN56, control terminals which areconnected to the second input, are connected to the second power sourceand the numbers of the switch elements operating as loads for the firstand second inputs are equal each other.

In a preferred embodiment of the present invention, shown in FIG. 7, thetiming averaging circuit includes a first switch element MP61 connectedacross the first power source VCC and a first internal node N71, a firstlogical circuit NAND 61 fed with first and second input signals IN1, IN2from an input end and having its output end connected to a controlterminal of the first switch element MP61, the first switch elementbeing turned on when both the first, and second input signals are at afirst value, a second switch element MN61 connected in series across thefirst internal node N71 and the second power source GND and being turnedoff or on when the first input signal is at the first or second value,respectively, a third switch element MN62 turned on or off when anoutput signal OUT is at the first or second value, respectively, afourth switch element MN63 connected in series across the first internalnode N71 and the second power source and being turned off or on when thefirst input signal is at the first or second value, respectively, afifth switch element MN64 turned on or off when an output signal OUT isat the first or second value, respectively, and a sixth switch elementMP66 connected across the first power source and a third internal nodeN73 for inputting the first internal node N71 to a control terminal.

The timing averaging circuit also includes a seventh switch element MN65connected across the second power source GND and the second internalnode N72,

a second logical circuit NOR61 fed with first and second input signalsIN1, IN2 and having its output end connected to a control terminal ofthe seventh switch element MN65, the seventh switch element MN65 beingturned on when both the first and second input signals IN1, IN2 are at asecond value, an eighth switch element MP64 connected in series acrossthe second internal node N72 and the first power source VCC and beingturned on or off when the first input signal is at the first or secondvalue, respectively, a ninth switch element MP62 turned off or on whenan output signal is at the first or second value, respectively, a tenthswitch element MP65 connected in series across the second internal nodeN72 and the first power source VCC and being turned on and on when thesecond input signal is at the first or second value, respectively, aneleventh switch element turned off or on when the output signal is atthe first or second value, respectively, a twelfth switch element MP63connected across the second power source and the third internal node forinputting the second internal node to a control terminal and an invertercircuit INV65 having its input terminal fed with the third internal nodeand an output logical value of which is determined by the relativemagnitudes of the third internal node potential and a threshold value.The clock control circuit further includes circuit means for on/offcontrolling a first switch element pair made up of the third switchelement MN65 and the fifth switch element MN64 and a second switchelement pair made up of the ninth switch element MP62 and the eleventhswitch element MP63.

The circuit means may, for example, be buffer circuits INV67, INV66 forgenerating normal signals of an output signal prescribed by the firstand second input signals IN1, IN2. An output of the buffer circuit isconnected in common to control terminals of the fifth switch elementMN65, fifth switch element MN64, ninth switch element MP62 and theeleventh switch element MP63.

In a preferred embodiment of the present invention, shown in FIG. 8, thetiming averaging circuit includes a first switch element MP71 connectedacross the first power source and a first internal node N81, a firstlogical circuit NAND71 fed with first and second input signals andhaving its output end connected to a control terminal of the firstswitch element MP71, the first switch element MP71 being turned on whenboth the first and second input signals are at a first value, second andthird switch elements MN71, MN72 connected in series across the firstinternal node N81 and the second power source, with the second switchelement MN71 being turned off or on when the first input signal is atthe first or second value, respectively. The timing averaging circuitalso includes a sixth switch element MP76 connected across the firstpower source and a third internal node N83 for inputting the firstinternal node N81 to a control terminal.

The timing averaging circuit also includes a seventh switch element MN75connected across the second power source GND and the second internalnode N82, a second logical circuit NOR71 fed with first and second inputsignals IN1, IN2 and having its output end connected to a controlterminal of the eleventh switch element MP72, MP73, the seventh switchelement being turned on when both the first and second input signals areat a second value, eighth and ninth switch elements MP74, MP72 connectedin series across the second internal node N82 and the first power sourceand being turned on or off when the first input signal is at the firstor second value, respectively, a ninth switch element turned off or onwhen an output signal is at the first or second value, respectively,tenth and eleventh switch elements MP75, MP73 connected in series acrossthe second internal node N82 and the first power source and being turnedon or off when the first input signal is at the first or second value,respectively, a twelfth switch element MN76 connected across the secondpower source and the third internal node N83 for inputting the secondinternal node to a control terminal and an inverter circuit INV75 havingits input terminal fed with the third internal node N83 and an outputlogical value of which is determined by the relative magnitudes of thethird internal node potential and a threshold value.

An output of the first logical circuit NAND71 is connected in common tocontrol terminals of the ninth switch element MP72 and the eleventhswitch element MP73, whilst an output of the second logical circuitNOR71 is connected in common to control terminals of the third switchelement MN72 and the fifth switch element MN73.

In a preferred embodiment of the present invention, shown in FIG. 11,the structure of multiplication circuits 15 ₁ to 15 ₄ includes afrequency dividing circuit 2 for frequency dividing input clocks forgenerating and outputting plural clocks of different phases (multi-phaseclocks), a period detection circuit 6 for detecting the period of theinput clocks, and a multi-phase clock multiplication circuit 5 fed withmulti-phase clocks output from the frequency dividing circuit forgenerating the multi-phase clocks as multiplied clocks. The multi-phaseclock multiplication circuit includes a plurality of timing differencedividing circuits 4 a outputting signals corresponding to the dividedtiming difference between two inputs and a plurality of multiplicationcircuits 4 b for multiplying and outputting outputs of two the timingdifference dividing circuits. The plural timing difference dividingcircuits includes a timing difference dividing circuit fed with the samephase clocks and a timing difference dividing circuit fed with outputsof two the timing difference dividing circuits.

In a preferred embodiment of the present invention, shown in FIG. 13,there are provided 2n timing difference dividing circuits for outputtingsignals obtained on dividing the timing difference of two input timings,the 2i-1st timing difference dividing circuit 208, 210, 212, 214, where1≦i≦n, is fed with an ith same clock as the two inputs, the 2ith timingdifference dividing circuit (209, 211, 213, 215), where 1≦i≦n, is fedwith the ith clock and (i+1 mod n)th clock, where mod denotes aremainder operation such that i+1 mod n means a remainder obtained ondividing I+1 with n, there being further provided 2n pulse widthcorrection circuits 216 to 223 fed with an output of a Jth timingdifference dividing circuit, where 1≦J≦2n, and with an output of atiming difference dividing circuit, as input, where J+2 mod n means aremainder resulting from division of J+2 by n, and n multiplicationcircuits 224 to 227 fed with an output of a Kth pulse width correctioncircuit, where 1≦K≦n, and an output of the (K+n)th pulse widthcorrection circuit, as inputs.

In a preferred embodiment of the present invention, shown in FIG. 15,the timing difference dividing circuit includes a logical circuit NOR14fed as input with first and second input signals and which sets theinternal node to the potential of a first power source when the firstand second input signals are at a first value, and a buffer circuit oran inverter circuit INV15 for changing the output logical valuedepending on the relative magnitudes of the potential of the internalnode as an output of the logical circuit and a threshold value, aplurality of series connected switch elements and capacitances areconnected in parallel across the internal node and the second powersource (MN51 and CAP51, MN52 and CAP52, and MN53 and CAP53). Thecapacitance to be added to the internal node being determined by periodcontrol signal coupled to a control terminal of the switch.

By providing a semiconductor integrated circuit with the clock controlcircuit according to the present invention, for supplying clocks to aclock synchronization circuit, phase-matched clocks can be supplied overthe entire clock propagation path.

For explanation of the above-described embodiments of the presentinvention in more detail, certain preferred embodiments of the presentinvention will be hereinafter explained with reference to the drawings.

FIG. 1 shows a structure of a preferred embodiment of the presentinvention. In the preferred embodiment of the present invention, shownin FIG. 1, a circuit comprised of a clock propagation path, folded onitself to constitute a forward route and a return route in which thetiming at a mid point of the forward and return routes is taken toadjust the delay induced in the clock path, includes a timing averagingcircuit for averaging the timing difference between respective pulses ofthe clock signals.

On the forward route 11 ₁ of the clock propagation path, the delay timefrom a point A to a reversing point 11 ₃ is a, the delay time from apoint B to the reversing point 11 ₃ is b, the delay time from a point Cto the reversing point 11 ₃ is c, and the delay time from a point D tothe reversing point 11 ₃ is d. On the return route 11 ₂ of the clockpropagation path, a point E is at the delay time d from reversing point11 ₃, a point F is at the delay time c from reversing point 11 ₃, apoint G is at the delay time b from reversing point 11 ₃, and a point His at the delay time a from reversing point 11 ₃.

The clocks input from an input buffer 12 to the forward route 11 ₁ ofthe clock propagation path is turned back (direction-reversed) at thereversing point 11 ₃ and propagate on the return route 112. Two clocksignals at points A and H are input to a timing averaging circuit 10 ₁,from which an output signal L, as an average of the two timingdifferences, is output. Similarly, two clock signals at points B and Gare input to a timing averaging circuit 10 ₂, from which an outputsignal L, as an average of the two timing differences, is output. Twoclock signals at points G and F are input to a timing averaging circuit10 ₃, from which an output signal J, as an average of the two timingdifferences, is output. Similarly, two clock signals at points D and Eare input to a timing averaging circuit 10 ₄, from which an outputsignal I, as an average of the two timing differences, is output.

FIG. 2 shows a timing diagram for illustrating the basic operation of anembodiment of the present invention shown in FIG. 1. The clockpropagation path is arranged in a turned-back fashion, as shown in FIG.1. The respective points A, B, C and D of the forward route 11 ₁ areadjacent to respective points H, G, F and E of the return route 11 ₂.Clock outputs are input to timing averaging circuits 10 ₁ to 10 ₄ whichthen output four timing difference signals each having a median valuebetween two clocks.

Since the median values of the timing signals 2 a, 2 b, 2 c and 2 d atthe respective neighboring points A-H, B-G, C-F and D-E are equal to thetiming at the reversing-back point 11 ₃, the output timings of outputsI, J, K and L of the timing averaging circuits become equal one another.

That is, referring to FIG. 2, the timing of a falling edge of an outputL of a timing averaging circuit 10 ₁ outputting an average value of thetiming difference 2 a of the adjacent point set A-H is (preset delaytime Cons)+(2 a/2)=Cons+a, with respect to the rising edge of the clockat point A. The preset delay time cons is the propagation delay timeproper to e.g., the timing averaging circuits 10 ₁ to 10 ₄.Specifically, the preset delay time cons is the propagation delay timefrom inputting a given signal to two inputs of the timing averagingcircuit until outputting of the resulting output signal.

An output K of a timing averaging circuit 10 ₂, fed with a clock from aneighboring point set B-G, rises after a delay time corresponding to adelay time (a−b) to the neighboring point B plus (preset delay timeCons)+(2 b/2) and rises after Cons+a as from the clock rising edge timepoint at the point A. An output J of a timing averaging circuit 10 ₃ andan output i of a timing averaging circuit 104 rise after time Cons=a asfrom the time point of the clock falling edge at point A, with thetimings of the rising edges of the signals I, J, K and L thus beingcoincident with one another.

FIGS. 3 and 4 illustrate the principle of the timing averaging circuit10 according to an embodiment of the present invention. Meanwhile, thetiming averaging circuit 10 is a timing difference dividing circuit(interpolator) for outputting a signal corresponding to the delay timeobtained on interior division of a timing difference of two inputsignals by a preset ratio a, wherein the ratio of the interior divisionis set to 0.5 to make equal division of the timing difference. It isnoted that the timing averaging circuit shown in FIG. 1 is constitutedby the timing difference division circuit.

Referring to FIG. 3 a, the timing difference division circuit (TMD)includes inverters INV1, INV2, inverting and outputting input signalsIN1, IN2, and p-channel MOS transistors MP1, MP2 having its source, gateand drain connected to a power source VCC, outputs of the inverters IN1,IN2 and to an internal node N1, respectively. The timing differencedivision circuit (TMD) also includes a buffer circuit BUF which has itsinternal node N1 connected to an input end and a logical output value ofwhich is changed when the potential of the internal node N1 is higher orlower than a threshold voltage, and a NOR circuit NOR1 fed with inputsignals IN1, IN2 to output the results of NOR operations. The timingdifference division circuit (TMD) also includes an N-channel MOStransistor MN1 having its drain, source and gate connected to theinternal node N1, ground potential GND and to the output end of the NORcircuit NOR1, respectively and a capacitor C connected across theinternal node N1 and the ground GND.

The timing difference division circuit (TMD) is shown in a block diagramof FIG. 3 b. It is noted that the timing averaging circuit outputs asignal corresponding to the delay time obtained on averaging the timingdifference of an input signal, with the ratio of the interior divisionof the timing averaging circuit being set to 0.5.

FIG. 4 c shows three timing difference division circuits (TMDs), ofwhich a first timing difference division circuit (TMD) has its twoinputs fed with the same input signal IN1 to issue an output signalOUT1. A second timing difference division circuit (TMD) is fed with theinput signals IN1, IN2 to issue an output signal OUT2, whilst a thirdtiming difference division circuit (TMD) has its two inputs fed with thesame input signals IN1, IN2 to issue an output signal OUT2. Of thesethree timing difference division circuits (TMDs), the second timingdifference division circuit (TMD), fed with the input signals IN1, IN2to output the output signal OUT2, has a structure shown in FIG. 3 a. Asfor the circuit structure having the first to third timing differencedivision circuits (TMDs), shown in FIG. 4C, reference should be made to,for example, a structure shown in FIG. 13 a.

Referring to FIG. 4 d, there is a timing difference T between the inputsignals IN1, IN2, with the first, third and second timing differencedivision circuits (TMDs) issuing an output signal OUT1 with delay timet1, an output signal OUT3 with delay time t3 and an output signal OUT2with delay time t2, respectively. The delay time t2 is obtained oninteriorly dividing the delay time t1 and the delay time t3.

Referring again to FIG. 3 a, when the input signals IN1, IN2 are low, anoutput of the NOR circuit NOR1 goes high, with the N-channel MOStransistor MN1 being fired, the node N1 being at a ground potential andwith an output of the buffer circuit BUF going low.

If, with the threshold voltage V of an output of the buffer circuit BUFbeing inverted to the high level, the same input signals IN1 are fed tothe two input terminals IN1, IN2, the outputs of the inverters IN1, IN2are low, both the p-channel MOS transistors MP1, MP2 being fired, andthe N-channel MOS transistor MN1 being turned off, with the node N1being charged with drain currents i1, i2. If charges of the node N1,that needs to be charged up to a point of reaching the threshold valueof the buffer circuit BUF is CV, where C and V denote the capacitanceand the voltage, respectively, the delay time t1 is given byt 1=CV/(i 1+i 2).

Referring to FIG. 3 a, if the input signal IN1 and the input signal IN2,rising with the delay of time T from the input signal IN1, are fed tothe two input terminals IN1, IN2, as shown in FIG. 4 c, an output of theinverter INV1 goes low at the time of rising of the input signal IN1, sothat only the p-channel MOS transistor MP1 is turned on, while theN-channel MOS transistor MN1 is turned off, with the node N1 beingcharged with the drain current it for a time duration T (charge at N1being i1T). As the input signal IN2 then goes high, an output of theinverter INV2 goes low, with the p-channel MOS transistors MP1, MP2being turned on, with the N-channel MOS transistor MN1 being turned off,so that the node N1 is charged with the drain currents i1+i2. If thecharge of the node N1 that needs to be charged up to a threshold valueof the buffer circuit BUF is CV, where C and V denote the capacitanceand the voltage, respectively, the delay time t2 is given by:t 2=T+(CV−i 1 T)/(i 1+i 2)=T+CV/(i 1+i 2)−i 1 T/(i 1+i 2)=T(i 2/(i 1+i2)+t 1.

If the drain currents i1, i2 of the p-channel MOS transistors MP1, MP2are equal to each other,t 2=(½)T+t 1.

If, in FIG. 3 a, the same input signals iN2, delayed by time T from theinput signal IN1, is fed to the two input terminals IN1, IN2,

t 3=T+CV/(i 1+i 2).

Thus, by charging the capacitance of the internal node N1 of the timingaveraging circuit shown in FIG. 3 a during the time T corresponding tothe timing difference of the two input clocks, by the p-channel MOStransistor MP1 fed with the input signal IN1, and by charging thecapacitance by the p-channel MOS transistor MP2 fed with the inputsignal IN2 and by the two p-channel MOS transistors, a time differenceof T/2, as an average value of the timing difference T of the inputsignals IN1 and IN2, is produced from the time ti as compared to a casewhere the same input signal IN1 is input from the outset for charging bythe two p-channel MOS transistors MP1, MP2.

So, the timing difference division circuit is termed “a timing averagingcircuit”.

According to an aspect of the present invention, without using a PLLcircuit and a DLL circuit, the delayed time difference in the clock path11 can be suppressed low.

If, in the timing averaging circuit, the timing difference between theclock which undergoes transition first and the clock which undergoestransition later is to be divided by a factor of ½ to output a signalwith an averaged timing difference, this is accomplished by equating theon-currents (drain currents) i1, i2 of the p-channel MOS transistorsMP1, MP2 of FIG. 3 a. It is noted that, by setting the ratio of theon-currents (drain currents) i1, i2 of the p-channel MOS transistorsMP1, MP2 of FIG. 3 a to, for example, m:1, where m>1, an output signalhaving a delay time corresponding to the division of the timingdifference T of two clocks by an optional interior division ratio.According to the present invention, this sort of the timing differencedivision circuit may be used as a timing averaging circuit fed with twoclocks at two points on the forward and return routes of the clockpropagation path. By so doing, such a case in which the delay timebetween a first time on the forward route and the reversing point is notequal to the delay time between the reversing point and a secondposition on the return route can be coped with to realize phase matchingof respective clocks output by the timing difference dividing circuit.

FIG. 5 shows a configuration of a second embodiment of the presentinvention. In this second embodiment, the clock path 11 is functionally“circular”, with a direction-reversing point serving as a beginningpoint of the clock route (i.e., return route). An output of the inputbuffer 12 is fed to a branched point on a clock propagation path betweena route A, B, C and D and a route E, F, G and H. Two clock signals atcorresponding points (i.e., pairing points) A and H forming aneighboring point pair are input to the timing averaging circuit 10 ₁ tooutput an output signal L corresponding to the average delay time of twotiming differences. Two clock signals at corresponding points B and Gare input to the timing averaging circuit 10 ₂ to output an outputsignal K corresponding to the average delay time of two timingdifferences. Two clock signals at corresponding points C and F are inputto the timing averaging circuit 10 ₃ to output an output signal Jcorresponding to the average delay time of two timing differences.Similarly, two clock signals at points D and E are input to the timingaveraging circuit 10 ₄ to output an output signal I corresponding to theaverage delay time of two timing differences.

It should be noted that in the embodiment shown in FIG. 5, two branchedroutes intersect each other at the reversing point. However, thesebranched routes may extend in parallel (specifically, anti-parallel)each other without intersection, which configuration provides also thesame advantage. The formulation shown in FIG. 5 has benefit ofsymmetrical arrangement of the clock path (routes) with respect to asymmetry line connecting the input point (branching point) and theintersecting point.S.

In the above-described embodiment (first embodiment) described withreference to FIG. 1, plural timing averaging circuits 10 ₁ to 10 ₄ arearranged along forward and return routes 11 ₁, 11 ₂ of the clockpropagation path basically extending in a unidirectional direction. Inthe present second embodiment, there are provided forward and returnroutes 11 _(A), 11 _(D) of the clock propagation path, arranged at adistance from each other, and plural timing averaging circuits 10 ₁ to10 ₄ arranged for extending along the rims of forward and return routes11 _(A) and 11 _(D), for enlarging an area which allows for arraying ofthe timing averaging circuit within a chip.

In the second embodiment of the present invention, the timing averagingcircuit 10 may be configured as shown for example in FIGS. 6 to 8. Thetiming averaging circuit 10, shown in FIGS. 6 to 8, averages the risingand falling timings of the clock signals. The timing averaging circuit,shown in FIG. 3 a, is configured for outputting a rising signalprescribed by the delay time obtained on equally dividing the timingdifference of the rising edges of the two clock signals. The timingaveraging circuit shown in any of FIGS. 6 to 8 may be applied withadvantage to a configuration of furnishing clocks to a circuit adaptedfor operating using both rising and falling edges.

The timing averaging circuit, shown in FIG. 6, is now explained.

Referring to FIG. 6, the timing averaging circuit includes a p-channelMOS transistor MP51, having its source connected to a source VCC, ap-channel MOS transistor MP2 having its source connected to a drain ofthe p-channel MOS transistor MP1, an n-channel MOS transistor MN51,having its drain connected to the drain of the p-channel MOS transistorMP2, and an n-channel MOS transistor MN52, having its drain connected tothe source of the n-channel MOS transistor MN51 and its source connectedto the ground potential, with the input IN1 being connected in common tothe gates of the p-channel MOS transistor MP1, MP2 and the n-channel MOStransistors MN51, MN52.

The timing averaging circuit includes a p-channel MOS transistor MP53,having its source connected to a source VCC, a p-channel MOS transistorMP54 having its source connected to a drain of the p-channel MOStransistor MP53, an n-channel MOS transistor MN53, having its drainconnected to the drain of the p-channel MOS transistor MP54, and ann-channel MOS transistor MN54, having its drain connected to the sourceof the n-channel MOS transistor MN53 and its source connected to theground potential, with the input IN1 being connected in common to thegates of the p-channel MOS transistor MP53 and to the n-channel MOStransistor MN54 and with the input IN2 being connected in common to thegates of the p-channel MOS transistor MP54 and the n-channel MOStransistor MN53.

The timing averaging circuit also includes a p-channel MOS transistorMP55, having its source connected to the source VCC, a p-channel MOStransistor MP56 having its source connected to a drain of the p-channelMOS transistor MP55 and having its drain connected to the source VCC, an-channel MOS transistor MN56, having its source connected to the drainof the n-channel MOS transistor MN56, having its source connected to thedrain of the n-channel MOS transistor MN56 and having its drainconnected to the ground, with the input IN2 being connected to the gatesof the p-channel MOS transistor MP55 and the n-channel MOS transistorMN56.

The junction points of the p-channel MOS transistor MP52 and then-channel MOS transistor MN51 is connected to an input end of theinverter INV5, while the junction points of the p-channel MOS transistorMP54 and the n-channel MOS transistor MN53 is connected to an input endof the inverter INV5, an output end of which is connected to an outputterminal OUT.

The p-channel MOS transistors MP55, MP66 and the n-channel MOStransistors MN55, MN56 are connected to an input end of the inverterINV5, an output of which is connected to the output terminal OUT.

The operation of the timing averaging circuit shown in FIG. 6 isexplained. When the input signal IN1 rises from the low level to thehigh level, static charges of the node M51 are discharged from the pathsof the n-channel MOS transistors MN51, NM52. When the input signal IN2rises after a time delay of T from the low level to the high level aftera time delay of T, static charges of the node N51 are discharged fromthe n-channel MOS transistors of the two paths of the n-channel MOStransistors (n-channel MOS transistors MN51, NM52 and the n-channel MOStransistors MN53, NM54) so that a rising signal corresponding to thedelay time obtained on averaging the timing difference T of the inputsignals IN1 and IN2 is output as an output signal, as described above.

When the input signal IN1 decays from the high level to the low level,the node 51 is charged from the path of the p-channel MOS transistorsMP51, MP52 in the on state. When the input signal IN2 decays with adelay of time T, the node N51 is charged through the p-channel MOStransistors of the two paths (p-channel MOS transistors MN51, NM52 andthe n-channel MOS transistors MN53, NM54) so that a decaying signalcorresponding to the delay time equal to the averaged timing differenceT between the input signals IN1, IN2 is output.

Since the input sequence of clocks IN1, IN2 is fixed in the timingaveraging circuit shown in FIG. 6, it is necessary to connect a point atwhich a signal arrives first to a point at which a signal needs to beinput first (IN1 of FIG. 6), in consideration of the arrangement of theclock path.

That is, if the timing averaging circuit shown in FIG. 6 is to be usedfor a timing averaging circuit 10 ₁ of FIG. 5, a point A at which asignal arrives first is an input end IN1, and a point H at which thesignal arrives with a time delay is connected to the input end IN2.

The reason is that, in the circuit configuration shown in FIG. 6, thenumber of transistors turned on and off by the inputs IN1, IN2 in thecharging/discharging path is not symmetrical. For example, in twocurrent paths across the source VCC and the internal node 52, (that isin the current paths of transistors MP51, MP52 and transistors MP53,MP54), the number of transistors turned on with the decaying of theinput IN1 is three (MP51, MP52 and MP53, of which MP51 and MP3 operateas a constant current source), whereas the number of the transistorsturned on with the decaying of the input IN2 is one (MP54), thustestifying to the non-symmetrical configuration with respect to theinputs IN1, IN2. In contrast with the timing averaging circuit of FIGS.7 and 8, explained next, the circuit configuration shown in FIG. 6 isnot provided with logical circuits for on/off control of a constantcurrent source transistor, so that the number of transistors can bediminished correspondingly.

FIG. 7 shows the configuration of another embodiment of the timingaveraging circuit according to the present invention. The timingaveraging circuit, shown in FIG. 7, can be used even in a case whereinthe clock inputting sequence is not determined at the outset. Moreover,inner transistors of NAND and NOR are used as parallel MOS transistors.

This timing averaging circuit, shown in FIG. 7, includes a NAND circuitNAND61, having the inputs IN1, IN2 as inputs, inverter circuits INV61,INV62 having the inputs IN1, IN2 as inputs, a p-channel MOS transistorMP61, having its source connected to the source VCC and also having itsgate connected to an output end of the NAND circuits NAND61. The timingaveraging circuit also includes an n-channel MOS transistor MN61, havingits drain connected to the drain of the p-channel MOS transistor MP61and having its gate connected to the output end of the inverter circuitINV61, and an n-channel MOS transistor MN62, having its drain connectedto the source of the p-channel MOS transistor MP61 and having its sourceconnected to the ground. The timing averaging circuit also includes ann-channel MOS transistor MN63 having its drain connected to the drain ofthe p-channel MOS transistor MP61 and having its gate connected to theoutput end of the inverter INV62, and an n-channel MOS transistor MN64having its drain connected to the source of the n-channel MOS transistorMN63, and also having its source and the gate grounded and connected tothe gate of the n-channel MOS transistor MN62, respectively.

The timing averaging circuit also includes a p-channel MOS transistorsMP62, MP63, each having its source connected to the power source VCC andhaving its gate connected together, and p-channel MOS transistors MP64,MP65, each having its source connected to the drains of the p-channelMOS transistors MP62, MP63, and each having its gate connected to outputends of the inverter circuits INV64, INV63 fed with the inputs IN1, IN2,and an n-channel MOS transistor MN65 having its drain connected to thedrains of the p-channel MOS transistors MP64, MP65 and having its gateconnected to the output end of the NOR circuit NOR61 fed with the inputsIN1, IN2. The gates of the p-channel MOS transistors MP62, MP63 areconnected in common to the gates of the n-channel MOS transistors MN62,MN64.

The drain of the p-channel MOS transistor MP61 is connected to the gateof the p-channel MOS transistor MP66, the source of which is connectedto the power source, while the drain of the p-channel MOS transistorMP66 is connected to the drain of the n-channel MOS transistor MN66,with the gate of the n-channel MOS transistor MN66 being connected tothe drain of the n-channel MOS transistor MN65, with the source of then-channel MOS transistor MN66 being grounded.

The junction point of the p-channel MOS transistor MP66 and then-channel MOS transistor MN66 is connected to the output terminal OUTthrough an inverter INV65, with an output of the inverter INV65 beingconnected through inverters INV66, INV67 to the common gate of then-channel MOS transistors MN62, MN64 and to the common gates of thep-channel MOS transistors MP62, MP63.

The operation of the timing averaging circuit shown in FIG. 7 isexplained.

In FIG. 7, when the input signals IN1, IN2 decay to the low level fromthe high level, an output terminal of the NAND circuit NAND 61 transitsfrom the low level to the high level to turn the p-channel MOStransistor MP61 off, while turning on one and then both of the n-channelMOS transistors MN61, 63, the gates of which are fed with outputs of theinverters INV61, INV62. Since the output OUT is as yet at a high level,prior to decaying, the output potential OUT is transmitted through theinverters INV67, INV66 to the node N74, so that the node N74 goes high.Since the n-channel MOS transistors MN62, 64, the gate input of each ofwhich is the node N74, are turned on, the node N71 is discharged, thepotential of the node N71 is lowered to turn on the p-channel MOStransistor MP66. The potential of the node 73 goes high so that adecaying signal from the high level to the low level is output throughthe inverter INV65. The output signal OUT has a delay time correspondingto the delay time equal to one half of the timing difference between theinput signals IN1, IN2. The output potential OUT of the inverter INV65is transmitted through the inverters INV67, INV66 to the node N74. Whenthe output potential OUT goes low, the n-channel MOS transistors MN62,64 are turned off to turn on the p-channel MOS transistors MP62, MP63.

The timing averaging circuit shown in FIG. 7 includes the NAND circuitNAND 61, and logical circuits in the form of the inverters INV61, INV62,and outputs a signal of a delay time corresponding to the averagedtiming difference between the input signals IN1, IN2, no matter which ofthe signals IN1, IN2 is advanced in phase relative to the other. (Theaveraged timing difference between the input signals IN1, IN2 is theaverage delay time between an output when an input is one of the inputsignals IN1 and IN2 which leads the other in phase and an output when aninput is one of the input signals IN1 and IN2 which lags the other inphase.)

Referring to FIG. 7, when the input signals IN1, IN2 rise from the lowlevel to the high level, an output of NOR circuit NOR61 decays from thehigh level to the low level to turn off the n-channel MOS transistorMN65 as well as to turn on one and then both of the p-channel MOStransistors MP64, MP65, the gates of which are fed with outputs of theinverters INV63, INV64. Since the output OUT is as yet at a low level,prior to rising, the output potential OUT is transmitted through theinverters INV66, INV67 to the node N74 to set the node N74 to a lowlevel to turn on the n-channel MOS transistors MN62, MN63 having thenode N74 as the gate input. This charges the node N72 to the low levelto raise its potential to turn on the n-channel MOS transistor MN66. Thenode N73 goes low so that a rising signal from the low level to the highlevel is output through the inverter INV65. As aforesaid, the outputsignal OUT has a delay time corresponding to one-half the timingdifference between the input signals IN1, IN2. The output potential OUTof the inverter INV65 is transmitted through the inverters INV66, INV67to the node N74. When the output potential OUT goes high, the n-channelMOS transistors MN62, MN63 are turned on, while the p-channel MOStransistors MP62, MP63 are turned off.

The timing averaging circuit shown in FIG. 7 also includes a NOR circuitNOR61, and logical circuits in the form of the inverters INV63, INV64,and outputs a signal of a delay time corresponding to the averagedtiming difference between the input signals IN1, IN2, no matter which ofthe signals IN1, IN2 is advanced in phase relative to the other. (Theaveraged timing difference between the input signals IN1, IN2 is theaverage delay time between an output when an input is one of the inputsignals IN1 and IN2 which leads the other in phase and an output when aninput is one of the input signals IN1 and IN2 which lags the other inphase.) The timing averaging circuit shown in FIG. 7 acquires controlsignals (gate signals) for turning on/off the n-channel MOS transistorsMN62, MN64 and p-channel MOS transistors MP62, MP63, operating as theconstant current source for charging/discharging the internal nodes N71,N72, from the logical value of the output signal OUT. The presentinvention is, however, not limited to this feedback configuration, andmay be appropriately modified, provided that, in discharging theinternal node N71, based on the first and second input signals IN1, IN2,the n-channel MOS transistors MN62, MN64 operating as the constantcurrent source are turned on, and that, in charging the internal nodeN72, the p-channel MOS transistors MP62, MP63 operating as the constantcurrent source are turned on.

FIG. 8 shows an exemplary modification of the timing averaging circuitshown in FIG. 7. This timing averaging circuit, shown in FIG. 8,includes a NAND circuit NAND71, having the inputs IN1, IN2 as inputs,inverter circuits INV61, INV62 having the inputs IN1, IN2 as inputs, ap-channel MOS transistor MP71, having its source connected to the sourceVCC and also having its gate connected to an output end of the inverterINV72. The timing averaging circuit also includes an n-channel MOStransistor MN73, having its drain connected to the drain of thep-channel MOS transistor MP71 and having its gate connected to theoutput end of the inverter circuit INV72, and an n-channel MOStransistor MN74, having its drain connected to the source of thep-channel MOS transistor MP73 and having its source and gate connectedto the ground and to the gate of the n-channel MOS transistor MN72.

The timing averaging circuit also includes a p-channel MOS transistorsMP72, MP73, each having its source connected to the power source VCC andhaving its gates connected together, and p-channel MOS transistors MP74,MP75, each having its source connected to the drains of the p-channelMOS transistors MP72, MP73, and each having its gate connected to outputends of the inverter circuits INV74, INV73 fed with the inputs IN1, IN2,and an n-channel MOS transistor MN75 having its drain connected to thedrains of the p-channel MOS transistors MP74, MP75 and having its gateconnected to the output end of the NOR circuit NOR71 fed with the inputsIN1, IN2. The gates of the p-channel MOS transistors MP74, MP75 areconnected in common to the gates of the n-channel MOS transistors MN72,MN73.

The drain of the p-channel MOS transistor MP71 is connected to the gateof the p-channel MOS transistor MP76, the source of which is connectedto the power source, while the drain of the p-channel MOS transistorMP76 is connected to the drain of the n-channel MOS transistor MN76,with the gate of the n-channel MOS transistor MN66 being connected tothe drain of the n-channel MOS transistor MN65, with the source of then-channel MOS transistor MN66 being grounded.

The junction point of the p-channel MOS transistor MP76 and then-channel MOS transistor MN76 is connected to the output terminal OUTthrough an inverter INV75.

The operation of the timing averaging circuit shown in FIG. 8 isexplained.

In FIG. 8, when the input signals IN1, IN2 decay to the low level fromthe high level, an output terminal of the NAND circuit NAND 71 transfersfrom the low level to the high level to turn the p-channel MOStransistor MP71 off, while turning on one and then both of the n-channelMOS transistors MN71, 73, the gates of which are fed with outputs of theinverters INV71, INV72. The node N81 is discharged, the potential of thenode N81 is lowered to turn on the p-channel MOS transistor MP76. Thepotential of the node 83 goes high so that a rising signal from the lowlevel to the high level is output through the inverter INV75. The outputsignal OUT has a delay time corresponding to the delay time equal to onehalf the timing difference between the input signals IN1, IN2.

Referring to FIG. 8, when the input signals IN1, IN2 rise from the lowlevel to the high level, an output of NOR circuit NOR71 decays from thehigh level to the low level to turn off the n-channel MOS transistorMN65 as well as to turn on one and then both of the p-channel MOStransistors MP74, MP75, the gates of which are fed with outputs of theinverters INV63, INV64. The node N82 is charged to the high level toraise its potential to turn on the n-channel MOS transistor MN76. Thenode N83 goes low so that a decaying signal from the high level to thelow level is output through the inverter INV75. As aforesaid, the outputsignal OUT has a delay time corresponding to one-half the timingdifference between the input signals IN1, IN2.

Referring to FIGS. 9 to 13, a third embodiment of the present inventionis explained. This embodiment renders it possible to apply the presentinvention to a configuration in which the delay on the clock propagationpath is longer than the clock period tCK. Recently, with the tendencytowards more variegated functions of the semiconductor integratedcircuit, the length of the clock propagation path tends to be increased,while the operating frequency is becoming higher. Thus, if, in theconfiguration of the above-described embodiment shown for example inFIG. 1, the delay quantity on the clock propagation path is longer thanthe clock period tCK, for example, if the delay time 2a between a pointA on the forward route 11 ₁ remotest from the reversing point 11 ₃ onthe clock propagation path and a point H on the return route 11 ₂ islonger than the clock period tCK, the following results. That is, in thetiming averaging circuit 10 ₁, to the fist and second inputs which areinput clocks from the points A and H, there is input, before a clockinput to the clock propagation path reaches the point H to be input tothe second input end, the clock of the next following clock cycle isinput to the point A, such that a desired average value cannot beoutput. The present third embodiment of the present invention renders itpossible to realize the desired operation when the delay on the clockpropagation path is longer than the clock period tCK.

Referring to FIG. 9, clocks from frequency division by a frequency 20dividing circuit 14 from the input buffer 12 are fed to the clockpropagation path (forward route 11 ₁, reversing point 11 ₃ and returnroute 11 ₂).

The clock signals from the input buffer 12 with a clock period tCK, arefrequency-divided by a frequency dividing circuit 14. The clocks inputto the clock propagation path 11 are turned on the clock propagationpath, with two clock signals at points A and H being fed to the timingaveraging circuit 10 ₁. An output signal L with the delay timecorresponding to a mean value of two timing differences is input to amultiplication circuit 15 ₁ which then outputs a multiplied signal P.Two clock signals at points B and G are fed to the timing averagingcircuit 10 ₂ which then outputs an output signal K with a delay timecorresponding to a mean value of the two timing differences to amultiplication circuit 15 ₂ to output a signal O. Two clock signals atpoints C and F are fed to a timing averaging circuit 10 ₃ which thenoutputs an output signal J with a delay time corresponding to a meanvalue of the two timing differences to a multiplication circuit 15 ₃ tooutput a multiplied signal N. Two clock signals at points D and E arefed to a timing averaging circuit 10 ₄ which then outputs an outputsignal I with a delay time corresponding to a mean value of the twotiming differences to a multiplication circuit 15 ₁ to output a signalM.

FIG. 10 shows a timing chart of the circuit shown in FIG. 9. The clocksare frequency-divided by the frequency dividing circuit 14 and thefrequency divided clocks are sent to the clock propagation path 11 onwhich the clocks are turned and sent over a bidirectional clocktransmission line. A mean value of the timings of the clock pulses istaken by the timing averaging circuit 10, an output of which ismultiplied by the multiplication circuit 15 to output a multipliedoutput.

According to the present invention, the multiplication circuit isrealized by the combination of timing averaging circuits. Thismultiplication circuit may be such a configuration proposed by thepresent inventors in JP Patent Applications JP-H-09-157042 (nowJP-A-11-004186) and JP-H-09-157028 (now JP-A-11-004145).

In the present embodiment, the delay magnitudes of the clock propagationpath can be matched solely by the timing averaging circuit, withoutusing a feedback circuit, if the delay magnitude on the clockpropagation path 11 is longer than the clock period tCK.

Referring to FIGS. 11 to 15, an exemplary configuration of themultiplication circuit 15 embodying the present invention is explained.Referring to FIG. 11, in this multiplication circuit is the clock oncefrequency divided to give multi-phase clocks, and the timings among twoconsecutive phases of the multi-phase clocks are averaged to produce anew clock by way of timing averaging. Thus, the clock multiplicationcircuit uses this new clock output and a clock of a non-averaged outputto double the number of phases, followed by synthesizing these clocks toperform clock multiplication.

In more detail, referring to FIG. 11, the multiplication circuit 15includes a frequency dividing circuit 2 for frequency dividing clocks 1(in an preferred embodiment of the present invention, an output of thetiming difference averaging circuit) to generate multi-phase clocks 3, amulti-phase clock multiplication circuit 5, fed with outputs 3 of thefrequency dividing circuit 2, a period detection circuit 6 made up of afixed number of stages of ring oscillators and a counter for countingthe number of oscillations of the ring oscillator during one clockperiod to detect the clock period and a clock synthesis circuit 8 forsynthesizing outputs the multi-phase clock multiplication circuit 5 togenerate multiplied clocks 9. The multi-phase clock multiplicationcircuit 5 includes plural timing difference dividing circuits 4 a foroutputting a signal corresponding to the interior division of timingdifferences of two input signals and plural multiplication circuits 4 bfor multiplying outputs of two timing difference dividing circuits.

The plural timing difference dividing circuits 4 a comprise timingdifference dividing circuits each fed with the same phase clocks andwith a timing difference dividing circuits each fed with two neighboringclocks. The period detection circuit 6 outputs a control signal 7 toadjust the load capacity of the timing difference dividing circuits 4 ain the multi-phase clock multiplication circuit 5 to control the clockperiod.

FIG. 12 shows a specified configuration of a multiplication circuit forgenerating four-phase clocks as illustration of the multiplicationcircuit 15. Referring to FIG. 12, the multiplication circuit includes a¼ frequency dividing circuit 201 for dividing the frequency of the inputclocks 204 by four for outputting four-phase clocks Q1 to Q4, nseries-connected four-phase clock multiplication circuits 202 ₁ to 202_(n), a lock synthesis circuit 203 and a period detection circuit 204.The final-stage four-phase clock multiplication circuit 202 _(n) outputs2n-multiplied four-phase clocks Qn1 to Qn4 which are synthesized by theclock synthesis circuit 203 to output frequency multiplied clocks 207.Meanwhile, the number of stages of the four-phase clock multiplicationcircuits is arbitrary.

A ¼ frequency dividing circuit 201 divides input clocks 205 by ¼ togenerate four-phase clocks Q1, Q2, Q3 and Q4, which then are multipliedby the four-phase clock multiplication circuit 202, to generatefour-phase clocks Q11 to Q14. Similarly, 2n-multiplied four-phase clocksQn1 to Qn4 are produced from the four-phase clock multiplication circuit202 _(n).

The period detection circuit 204 is made up of a fixed number of stagesof ring oscillators, and a counter. During one period of the clocks, theperiod detection circuit 204 counts the number of oscillations of thering oscillators to output a control signal 206 according to the numberof counts to adjust the load in the four-phase clock multiplicationcircuit 202. This period detection circuit 204 eliminates variations inthe operating range of clock periods and device characteristics.

The four-phase clocks are rendered into eight phase clocks by thefour-phase clock multiplication circuit 202 and again rendered back intofour phase clocks for continuous frequency multiplication.

FIG. 13 shows an illustrative structure of the four-phase clockmultiplication circuit 202 _(n). It is noted that the four-phase clockmultiplication circuits 202 ₁ to 202 _(n) shown in FIG. 12 are all ofthe same structure.

Referring to FIG. 13 a, this four-phase clock multiplication circuit 202_(n) is made up of eight timing difference dividing circuits 208 to 215,eight pulse width correction circuits 216 to 23 and four multiplicationcircuits 224 to 227. FIG. 13 b shows the structure of a pulse widthcorrection circuit comprised of a NAND circuit fed with a signalcomprised of a second input T23 inverted by the inverter IN2 and withthe first input T21 as inputs.

FIG. 13 c shows a structure of a multiplexing circuit comprised of a2-input NAND circuit.

FIG. 14 shows a signal waveform diagram for illustrating the timingoperation of the four-phase clock multiplication circuits 202. Therising of the clock T21 is determined by the delay corresponding to theinternal delay of the timing difference dividing circuit 208, the risingof the clock t22 is determined by the timing division by the timingdifference dividing circuit 209 of the rising timing of the clock Q(n−1)1 and the rising of the clock Q(n−1) 2 and the delay caused by theinternal delay, and the rising of the clock T23 is determined by thetiming division by the timing difference dividing circuit 209 of therising timing of the clock Q(n−1) 1 and the rising of the clock Q(n−1) 2and the delay caused by the internal delay. In similar manner, therising of the clock t26 is determined by the timing division by thetiming difference dividing circuit 213 of the rising timing of the clockQ(n−1) 3 and the rising of the clock Q(n−1) 4 and the delay caused bythe internal delay, and the rising of the clock T27 is determined by thetiming division by the timing difference dividing circuit 214 of therising timing of the clock Q(n−1) 4 and the rising of the clock Q(n−1) 1and the delay caused by the internal delay.

The clocks T21 and t23 are fed to the pulse width correction circuit 216which then outputs a pulse P21 having a falling edge determined by theclocks T21 and a falling edge determined by the clock T23. By a similarsequence of operations, pulses P22 to P28 are generated, with the clocksP21 to P28 becoming 25% duty eight-phase pulses with dephasing of 45degrees. The clock P25 dephased by 180 degrees from the clock P21undergoes demultiplication in a multiplication circuit 224 so as to beoutput as 25-% duty clocks Qn1. In similar manner, clocks Qn2 to Qn4 aregenerated. The clocks Qn1 to Qn4 become 50% duty four-phase pulses,dephased 90 degrees each. The periods of the clocks Qn1 to Qn4 aremultiplied in frequency by two as clocks Qn1 to Qn4 are generated fromthe clocks Q(n−1) 1 to (n01) 4.

FIGS. 15 a and 15 b show the show illustrative structures of timingdifference dividing circuits 208, 209 shown in FIG. 13. These circuitsare at the same configuration and differ as to whether two inputs arethe same signals or two neighboring signals are input. That is, thetiming difference dividing circuit 208 and the timing differencedividing circuit 209 are at the same configuration except that, in theformer, the same input Q(n−1) 1 is fed to a two-input NOR circuit NOR14,whereas, in the later, input Q(n−1) 1 and Q(n−1) 2 are fed to thetwo-input NOR circuit NOR14. The two-input NOR circuit NOR14 is made upof two p-channel MOS transistors connected in series across the powersource VCC and the output end and the gates of which are fed with theinput signals IN1, IN2 and two n-channel MOS transistors connected inparallel across the input end and the ground and the gates of which arefed with the input signals IN1, IN2.

An internal node N51 (N61) as an output node of the two-input NORcircuit NOR14 is connected to an input end of the inverter 1N2 15.Across the internal node and the ground, there is connected a parallelcircuit of a circuit comprised of a series connection of a n-channel MOStransistor MN51 and a capacitance CAP51, a series connection of an-channel MOS transistor MN52 and a capacitance CAP52 and a seriesconnection of a n-channel MOS transistor MN53 and a capacitance CAP53.To the gates of the respective n-channel MOS transistors MN51 to 53 iscoupled the control signal 7 from the period detection circuit 6 to turnthe transistors on or off. The size ratio of the gate widths of then-channel MOS transistors MN51 to 53 to the capacitances CAP51 to 53 isset to, for example, 1:2:4. The load connected to the common node isadjusted in eight stages to set the clock period.

Turning to the timing difference dividing circuit 208, static charges ofthe node N51 are extracted through a n-channel MOS transistor of theNOR14. When the potential of the node N51 reaches the threshold value ofthe inverter IN2 15, there rise clocks T21, as output of the inverterINV15. If the static charges of the node N51, that need to be extractedwhen the threshold value of the inverter INV15 is reached, are denotedCV, where C and V denote the capacitance and the voltage, respectively,and the discharging current by the n-channel MOS transistor of the NOR14is denoted I, the static charges of CV are discharged with the currentvalue 21, as a result of which the time CV/2I represents the timingdifference (propagation delay time) as from the rising edge of the clockQ(n−1) 1 until the rising of the clock T21. When the clock Q(n−1) 1 islow, an output node N51 of the two-input NOR circuit NOR14 is charged tothe high level, with the output clock T21 of the inverter INV15 beingthen at a low level.

As for the timing difference dividing circuit 209, static charges of thenode N61 are extracted by the NOR14 after time tCKn (tCKn=multi-phaseclock period) from the rising edge of the clock Q(n−1). The edge of theclock T22 rises when, after time tCKn, the potential of the node n61reaches the threshold value of the inverter INV15 from the rising edgeof the clock Q(n−1). If the static charges of the node N61 are denotedCV, and the discharge current of the n-MOS transistor of the two-inputNOR circuit NOR14 is I, static charges CV are discharged from the risingof the clock Q(n−1) 1 with the current I during the time period tCKn,and extraction is made with the current 2I during the remaining period.So, the timetCKn+(CV−tCKn I)/2I=CV/2I+tCKn/2

represents the timing difference of the rising edge of the clock T22from the rising edge of the clock Q(n−1) I.

That is, the rising timing difference between clocks T22 and T21 istCKn/2.

If the clock Q(n−1) 1 and the clock Q(n−1) 2 are both low and the outputnode N61 of the two-input NOR circuit NOR14 is charged through a pMOStransistor of the NOR14 from the power source to a high level, the clockT22 rises. The same situation holds for the clocks T22 to T28, with thetiming difference between the rising edges of the clocks T21 to T28being tCKn/2.

The pulse width correction circuits 216 to 223 generate 25% duty 8-phasepulses A23 to T28, dephased 45 degrees relative to one another.

The multiplexing circuits 224 to 227 generate 50% duty 4-phase pulsesQn1 to Qn4, dephased 45° relative to one another.

Referring to FIGS. 16 to 18, a fourth embodiment of the presentinvention is now explained. In the present embodiment, the presentinvention is applied to a configuration in which the delay magnitude onthe clock path is longer than the clock period tCK.

Referring to FIG. 16, showing the fourth embodiment of the presentinvention, clocks are first supplied to a direction-reversedbi-directional clock propagation path. In each neighboring point pair inthe forward route 11 ₁ and return route 11 ₁ are frequency divided intiming averaging circuits 100 ₁ to 100 ₄ provided with the frequencydividing function. The clock pulse timings of the frequency dividedclocks are averaged using the timing averaging circuits and subsequentlysynthesized by synthesis circuits 16 ₁ to 16 ₄. The clocks input to theclock propagation path 11 are direction-reversed on the clockpropagation path, such that two clock signals at points A and H are fedto the timing averaging circuit 100 ₁ provided with the frequencydividing function to generate output signals L1 to L4 with the delaytime corresponding to the mean value of two timing differences of thefrequency divided clocks, with the output signals L1 to L4 beingsynthesized by the synthesis circuit 16 ₁ to output a signal P.Similarly, two clock signals at points B and G are fed to the timingaveraging circuit 100 ₂ provided with the frequency dividing function togenerate output signals L1 to L4 with the delay time corresponding tothe mean value of two timing differences of the frequency dividedclocks, with the output signals K1 to K4 being synthesized by thesynthesis circuit 16 ₂ to output a signal O, and two clock signals atpoints C and F are fed to the timing averaging circuit 100 ₃ providedwith the frequency dividing function to generate output signals J1 to J4with the delay time corresponding to the mean value of two timingdifferences of the frequency divided clocks, with the output signals J1to J4 being synthesized by the synthesis circuit 16 ₃ to output a signalN, while two clock signals at points D and E are fed to the timingaveraging circuit 100 ₄ provided with the frequency dividing function togenerate output signals I1 to I4 with the delay time corresponding tothe mean value of two timing differences of the frequency dividedclocks, with the output signals I1 to I4 being synthesized by thesynthesis circuit 16 ₄ to output a signal M.

FIG. 17 shows the configuration of the timing averaging circuit 100 ₁provided with the frequency dividing function. The remaining timingaveraging circuits 100 ₂ to 100 ₄ provided with the frequency dividingfunction are configured in a similar fashion. The signals A1 to A4,obtained on frequency division of the clock at point A on the clockpropagation path 11 by a frequency dividing circuit 101 ₁ are sent totiming averaging circuit 102 ₁ to 102 ₄, while the signals B1 to B4,obtained on frequency division of the clock at point H on the clockpropagation path 11 by a frequency dividing circuit 101 ₂ are sent tothe timing averaging circuit 102 ₁ to 102 ₄. The timing averagingcircuit 102 ₁ outputs a median (mean) value signal L1 of the timingdifferences of A1 and B1, while the timing averaging circuit 102 ₂outputs a median value signal L2 of the timing differences of A2 and B2.In similar manner, the timing averaging circuit 102 ₄ outputs a medianvalue of the timing differences of A4 and B4, whilst the synthesiscircuits 16 synthesizes signals 11 to 14 to output a signal P.

Thus, in the present embodiment, the clocks of each point of the forwardroute 11 ₁ and the return route 11 ₁ of the clock propagation path arefrequency divided by four in the frequency dividing circuits 101 ₁, 101₂ to generate four-phase clocks to generate four signals obtained onaveraging the timing differences of the two corresponding frequencydivided clocks in the timing averaging circuit, these four signals beingsynthesized to one signal P by the synthesis circuit 16. Since theoutput of the synthesis circuit 16 is equivalent to the multiplexedoutput, the delay magnitude of the clock path can be matched solely bythe timing averaging circuits 100 ₁ to 100 ₄ provided with the frequencydividing function, without using the multiplexing circuit, even if thedelay magnitude on the clock propagation path of the frequency dividedclocks is longer than the clock period. The circuit scale of the presentembodiment not provided with the multiplexing circuit is at a smallercircuit scale than the one of the third embodiment.

FIG. 18 shows a timing chart illustrating the operation of a fourthembodiment of the present invention.

The frequency dividing circuits 101 ₁, 101 ₂ fed with signals at pointsA and H output signals A1 to A4 and B1 to B4 obtained on frequencydivision by four, with the timing averaging circuit 102 ₁ outputting asignal corresponding to a mean value of the timing differences of thesignals A1 and B1, with the timing of the post-synthesized outputsignals M to P being corresponding with one another.

Referring to FIGS. 19 and 20, a fifth embodiment of the presentinvention is explained. In the present embodiment the present inventionis applied to a configuration in which the delay magnitude on the clockpropagation path is longer than the clock period tCK.

Referring to FIG. 19, showing the fifth embodiment of the presentinvention, input clocks 13 are frequency divided by the frequencydividing circuit 14, and multi-phase (four-phase) clocks output by thefrequency dividing circuit 14 are output into clock wirings 11-1 to11-4. The clock wirings equal in number to the number of phases of theclocks are direction-reversed to serve as bi-directional clocktransmission lines. The timings of the clocks on the wirings of the eachphases are averaged, using the timing averaging circuit (TM), andsubsequently synthesized in the synthesis circuit 16.

The present fifth embodiment includes four timing averaging circuits(TM), fed with signals on paired points A1 to A4 on the forward routeand on paired points H1 to H4 on the return route of the same clockpropagation paths 11-1 to 11-4 to generate output signals L1 to L4, asynthesis circuit 16 ₁ for synthesizing the L1 to L4 to generate anoutput signal P, four timing averaging circuits (TM), fed with signalson paired points B1 to B4 on the forward route and on paired points G1to G4 on the return route of the same clock propagation paths 11-1 to11-4 to generate output signals K1 to K4, a synthesis circuit 16 ₂ forsynthesizing the K1 to K4 to generate an output signal O, four timingaveraging circuits (TM), fed with signals on paired points C1 to C4 onthe forward route and on paired points F1 to F4 on the return route ofthe same clock propagation paths 11-1 to 11-4 to generate output signalsJ1 to J4, a synthesis circuit 16 ₃ for synthesizing the J1 to J4 togenerate an output signal N, four timing averaging circuits (TM), fedwith signals on paired points D1 to D4 on the forward route and onpaired points E1 to E4 on the return route of the same clock propagationpaths 11-1 to 11-4 to generate output signals I1 to I4, and a synthesiscircuit 16 ₄ for synthesizing the I1 to I4 to generate an output signalM. In the present embodiment the outputs M to P are phase-matchedrelative to one another.

In the present embodiment, similarly to the above-described fourthembodiment, the delay magnitude of the clock path can be matched solelyby the timing averaging circuit, without using the multiplexing circuit,in a case wherein the delay magnitude on the clock propagation path islonger than the clock period. In the above-described fourth embodiment,the timing averaging circuits provided with the frequency dividingfunction are provided with two frequency dividing circuits. In thepresent embodiment, provided with the frequency dividing circuit 14 forfrequency dividing the input clocks 13 to furnish the resultingfrequency divided clocks to the four clock propagation paths 11-1 to11-4, the delay magnitudes of the clock paths can be matched with asmaller number of frequency dividing circuits. That is, although thenumber of wirings for the clock propagation paths is increased, thecircuit scale can be reduced as compared to that in the fourthembodiment.

A sixth embodiment of the present invention is explained with referenceto FIG. 21. The present sixth embodiment uses a timing averaging circuitTM and two layers of the clock pulse timing averaging circuits tofurnish the clock propagation path in a mesh-like fashion. Referring toFIG. 21, timing averaging circuits 110 ₁ to 110 ₄ for averaging thetimings at preset points on the forward and return routes of the clockpropagation path 111 adapted for propagating the clocks from the inputbuffer 112 are provided on one side of a chip. A plurality of circuitsfor averaging the clock pulse timings, fed with outputs of buffers 113 ₁to 113 ₄, fed in urn with outputs of the timing averaging circuit 110 ₁to 110 ₄, are arranged in parallel from the wirings correspondinglinearly in timing, and outputs are connected in a meshed fashion.

In the present sixth embodiment, clock signals can be supplied in whichthe delay magnitudes on the clock path are corresponding on the entirechip in a two-dimensional fashion in a semiconductor integrated circuit.That is, the clock timing supplied to the clock-using circuitry, such assynchronization circuit, on the entire chip area can be matched, nomater where the clock using circuitry is arranged on the chip layoutsurface.

In the timing averaging circuit of the sixth embodiment of the presentinvention, employing the circuit components similar to those of thefourth embodiment, it is possible to cope with a configuration in whichthe delay magnitude of the clock path is longer than the clock period.

According to the present invention, as described above, the phases ofthe clocks furnished in the internal circuit of the semiconductorintegrated circuit furnished with clocks can be matched in phase in ashort time and is suitably used for clock synchronization control in alarge-scale integrated circuit. Moreover, the present invention can beapplied to clock control of a substrate or a variety of devices withoutbeing limited to the semiconductor integrated circuit.

The meritorious effects of the present invention are summarized asfollows.

According to the present invention, as described above, there may beprovided a circuit in which the wiring delay in a direction-reversedbi-directional clock propagation path to eliminate the delay differenceon the clock transmission line in its entirety, wherein the delaydifficult may be eliminated in a shorter time.

The reason is that the timing is corresponding using a timing averagingcircuit without using PLL or DLL to overcome the problem that a longclock cycle is needed until elimination of the delay difference.

According to the present invention, the circuit scale may be preventedfrom being increased.

The reason is that, in the present invention, phase comparators orconcatenated delay circuits are eliminated in contradistinction from theconventional apparatus provided with plural phase comparators or pluralconcatenated delay circuits etc.

It should be noted that other objects, features and aspects of thepresent invention will become apparent in the entire disclosure and thatmodifications may be done without departing the gist and scope of thepresent invention as disclosed herein and claimed as appended herewith.

Also it should be noted that any combination of the disclosed and/orclaimed elements, matters and/or items may fall under the modificationsaforementioned.

1. A clock controlling circuit comprising: a timing averaging circuitprovided with a frequency dividing function for frequency dividing firstand second clocks, including the first clock from a first position on aforward route of a clock propagation path fed with input clocks at oneend and direction-reversing the input clocks and the second clock from asecond position corresponding to said first position to generatefrequency divided multi-phase clocks of plural different phases, saidtiming averaging circuit outputting a signal of a delay timecorresponding to a time equally dividing a timing difference betweenfrequency divided clocks having a corresponding phase among clocksignals obtained on frequency division of said two clocks; and asynthesis circuit for synthesizing plural outputs of said timingaveraging circuit into one signal and for outputting said one signal. 2.The clock controlling circuit as defined in claim 1 wherein a delay timebetween said first position and the direction-reversing point of saidclock propagation path is equal to a delay time between saiddirection-reversing point of said clock propagation path and said secondposition, and wherein a plurality of said timing averaging circuitshaving the frequency dividing function are arranged along a path betweena clock input end and a direction-reversing point of said clockpropagation path.